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LTC3406 LTC3406-1.5/LTC3406-1.8 1.5MHz, 600mA Synchronous Step-Down Regulator in ThinSOT
FEATURES

DESCRIPTIO
High Efficiency: Up to 96% Very Low Quiescent Current: Only 20A During Operation 600mA Output Current 2.5V to 5.5V Input Voltage Range 1.5MHz Constant Frequency Operation No Schottky Diode Required Low Dropout Operation: 100% Duty Cycle 0.6V Reference Allows Low Output Voltages Shutdown Mode Draws 1A Supply Current Current Mode Operation for Excellent Line and Load Transient Response Overtemperature Protected Low Profile (1mm) ThinSOTTM Package
The LTC (R)3406 is a high efficiency monolithic synchronous buck regulator using a constant frequency, current mode architecture. The device is available in an adjustable version and fixed output voltages of 1.5V and 1.8V. Supply current during operation is only 20A and drops to 1A in shutdown. The 2.5V to 5.5V input voltage range makes the LTC3406 ideally suited for single Li-Ion battery-powered applications. 100% duty cycle provides low dropout operation, extending battery life in portable systems. Automatic Burst Mode(R) operation increases efficiency at light loads, further extending battery life. Switching frequency is internally set at 1.5MHz, allowing the use of small surface mount inductors and capacitors. The internal synchronous switch increases efficiency and eliminates the need for an external Schottky diode. Low output voltages are easily supported with the 0.6V feedback reference voltage. The LTC3406 is available in a low profile (1mm) ThinSOT package.
, LTC and LT are registered trademarks of Linear Technology Corporation. Burst Mode is a registered trademark of Linear Technology Corporation. ThinSOT is a trademark of Linear Technology Corporation. Protected by U.S. Patents, including 6580258, 5481178.
APPLICATIO S

Cellular Telephones Personal Information Appliances Wireless and DSL Modems Digital Still Cameras MP3 Players Portable Instruments
TYPICAL APPLICATIO
VIN 2.7V TO 5.5V 4 CIN** 4.7F CER 1 3
95 90
2.2H* COUT 10F CER 5
3406 F01a
VIN = 2.7V
EFFICIENCY (%)
VIN
SW
VOUT 1.8V 600mA
85 VIN = 3.6V 80 VIN = 4.2V 75 70 65 60 0.1 VOUT = 1.8V 1 10 100 OUTPUT CURRENT (mA) 1000
3406 F01b
LTC3406-1.8 RUN VOUT 2
GND
*MURATA LQH32CN2R2M33 **TAIYO YUDEN JMK212BJ475MG TAIYO YUDEN JMK316BJ106ML
Figure 1a. High Efficiency Step-Down Converter
Figure 1b. Efficiency vs Load Current
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LTC3406 LTC3406-1.5/LTC3406-1.8
ABSOLUTE
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RATI GS
Input Supply Voltage .................................. - 0.3V to 6V RUN, VFB Voltages ..................................... - 0.3V to VIN SW Voltage .................................. - 0.3V to (VIN + 0.3V) P-Channel Switch Source Current (DC) ............. 800mA N-Channel Switch Sink Current (DC) ................. 800mA
PACKAGE/ORDER I FOR ATIO
TOP VIEW RUN 1 GND 2 SW 3 4 VIN 5 VFB
ORDER PART NUMBER LTC3406ES5 S5 PART MARKING LTA5
RUN 1 GND 2 SW 3
S5 PACKAGE 5-LEAD PLASTIC TSOT-23
TJMAX = 125C, JA = 250C/ W, JC = 90C/ W
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
The denotes specifications which apply over the full operating temperature range, otherwise specifications are TA = 25C. VIN = 3.6V unless otherwise specified.
SYMBOL IVFB VFB PARAMETER Feedback Current Regulated Feedback Voltage LTC3406 (Note 4) TA = 25C LTC3406 (Note 4) 0C TA 85C LTC3406 (Note 4) -40C TA 85C VIN = 2.5V to 5.5V (Note 4) LTC3406-1.5, IOUT = 100mA LTC3406-1.8, IOUT = 100mA VIN = 2.5V to 5.5V VIN = 3V, VFB = 0.5V or VOUT = 90%, Duty Cycle < 35%
CONDITIONS
VFB VOUT VOUT IPK VLOADREG VIN IS
Reference Voltage Line Regulation Regulated Output Voltage Output Voltage Line Regulation Peak Inductor Current Output Voltage Load Regulation Input Voltage Range Input DC Bias Current Active Mode Sleep Mode Shutdown Oscillator Frequency RDS(ON) of P-Channel FET RDS(ON) of N-Channel FET SW Leakage
(Note 5) VFB = 0.5V or VOUT = 90%, ILOAD = 0A VFB = 0.62V or VOUT = 103%, ILOAD = 0A VRUN = 0V, VIN = 4.2V VFB = 0.6V or VOUT = 100% VFB = 0V or VOUT = 0V ISW = 100mA ISW = -100mA VRUN = 0V, VSW = 0V or 5V, VIN = 5V
fOSC RPFET RNFET ILSW
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(Note 1)
Peak SW Sink and Source Current ........................ 1.3A Operating Temperature Range (Note 2) .. - 40C to 85C Junction Temperature (Note 3) ............................ 125C Storage Temperature Range ................ - 65C to 150C Lead Temperature (Soldering, 10 sec)................. 300C
TOP VIEW 5 VOUT 4 VIN
ORDER PART NUMBER LTC3406ES5-1.5 LTC3406ES5-1.8 S5 PART MARKING LTD6 LTC4
S5 PACKAGE 5-LEAD PLASTIC TSOT-23
TJMAX = 125C, JA = 250C/ W, JC = 90C/ W
MIN 0.5880 0.5865 0.5850 1.455 1.746 0.75
TYP 0.6 0.6 0.6 0.04 1.500 1.800 0.04 1 0.5
MAX 30 0.6120 0.6135 0.6150 0.4 1.545 1.854 0.4 1.25
UNITS nA V V V %/V V V %/V A %

2.5 300 20 0.1 1.2 1.5 210 0.4 0.35 0.01
5.5 400 35 1 1.8 0.5 0.45 1
V A A A MHz kHz A
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LTC3406 LTC3406-1.5/LTC3406-1.8
ELECTRICAL CHARACTERISTICS
The denotes specifications which apply over the full operating temperature range, otherwise specifications are TA = 25C. VIN = 3.6V unless otherwise specified.
SYMBOL VRUN IRUN PARAMETER RUN Threshold RUN Leakage Current CONDITIONS

MIN 0.3
TYP 1 0.01
MAX 1.5 1
UNITS V A
Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: The LTC3406E is guaranteed to meet performance specifications from 0C to 70C. Specifications over the -40C to 85C operating temperature range are assured by design, characterization and correlation with statistical process controls.
Note 3: TJ is calculated from the ambient temperature TA and power dissipation PD according to the following formula: LTC3406: TJ = TA + (PD)(250C/W) Note 4: The LTC3406 is tested in a proprietary test mode that connects VFB to the output of the error amplifier. Note 5: Dynamic supply current is higher due to the gate charge being delivered at the switching frequency.
TYPICAL PERFOR A CE CHARACTERISTICS
(From Figure1a Except for the Resistive Divider Resistor Values) Efficiency vs Input Voltage
100 95 90 IOUT = 100mA IOUT = 10mA
EFFICIENCY (%)
85 IOUT = 1mA
EFFICIENCY (%)
80 75 70 65 60 55 50 VOUT = 1.8V 2 3
IOUT = 600mA
80 75 70 65 60 0.1
VIN = 4.2V VIN = 3.6V
EFFICIENCY (%)
IOUT = 0.1mA
4 5 INPUT VOLTAGE (V)
Efficiency vs Output Current
100 95 90
EFFICIENCY (%)
VOUT = 2.5V VIN = 2.7V REFERENCE VOLTAGE (V) VIN = 3.6V
85 80 75 70 65 60 0.1 10 100 1 OUTPUT CURRENT (mA) 1000
3406 G04
0.604 0.599 0.594 0.589 0.584 -50 -25
FREQUENCY (MHz)
VIN = 4.2V
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3406 G01
Efficiency vs Output Current
95 90 85 VOUT = 1.2V VIN = 2.7V 95 90 85
Efficiency vs Output Current
VOUT = 1.5V VIN = 2.7V VIN = 4.2V 80 VIN = 3.6V 75 70 65 60 0.1
1 10 100 OUTPUT CURRENT (mA)
1000
3406 G02
1 10 100 OUTPUT CURRENT (mA)
1000
3406 G03
Reference Voltage vs Temperature
0.614 VIN = 3.6V 0.609 1.65 1.60 1.55 1.50 1.45 1.40 1.35 50 25 75 0 TEMPERATURE (C) 100 125 1.70
Oscillator Frequency vs Temperature
VIN = 3.6V
1.30 -50 -25
50 25 75 0 TEMPERATURE (C)
100
125
3406 G05
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LTC3406 LTC3406-1.5/LTC3406-1.8 TYPICAL PERFOR A CE CHARACTERISTICS
(From Figure1a Except for the Resistive Divider Resistor Values) Oscillator Frequency vs Supply Voltage
1.8
OSCILLATOR FREQUENCY (MHz)
1.7
OUTPUT VOLTAGE (V)
1.6 1.5 1.4 1.3 1.2
1.814 1.804 1.794 1.784 1.774
RDS(ON) ()
2
3 4 5 SUPPLY VOLTAGE (V)
RDS(ON) vs Temperature
0.7 VIN = 2.7V 0.6 VIN = 4.2V 0.5
RDS(ON) ()
VIN = 3.6V
SUPPLY CURRENT (A)
SUPPLY CURRENT (A)
0.4 0.3 0.2 0.1 0 -50 -25 MAIN SWITCH SYNCHRONOUS SWITCH 50 25 75 0 TEMPERATURE (C) 100 125
Switch Leakage vs Temperature
300 VIN = 5.5V RUN = 0V 250
SWITCH LEAKAGE (nA)
SWITCH LEAKAGE (pA)
200 150 100 50 0 -50 -25 MAIN SWITCH SYNCHRONOUS SWITCH
50 25 75 0 TEMPERATURE (C)
4
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3406 G07
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Output Voltage vs Load Current
1.844 1.834 1.824 VIN = 3.6V
RDS(ON) vs Input Voltage
0.7 0.6 0.5 0.4 0.3 0.2 0.1 0 0 1 5 4 2 3 INPUT VOLTAGE (V) 6 7
3406 G09
MAIN SWITCH
SYNCHRONOUS SWITCH
0
100 200 300 400 500 600 700 800 900 LOAD CURRENT (mA)
3406 G08
Supply Current vs Supply Voltage
50 45 40 35 30 25 20 15 10 5 0 2 4 3 5 SUPPLY VOLTAGE (V) 6
3406 G11
Supply Current vs Temperature
50 VIN = 3.6V 45 VOUT = 1.8V = 0A I 40 LOAD 35 30 25 20 15 10 5 0 -50 -25 50 25 0 75 TEMPERATURE (C) 100 125
VOUT = 1.8V ILOAD = 0A
3406 G12
Switch Leakage vs Input Voltage
120 100 80 60 40 20 0 SYNCHRONOUS SWITCH RUN = 0V SW 5V/DIV VOUT 100mV/DIV AC COUPLED IL 200mA/DIV
Burst Mode Operation
MAIN SWITCH
VIN = 3.6V VOUT = 1.8V ILOAD = 50mA 0 1 2 3 4 INPUT VOLTAGE (V) 5 6
3406 G14
4s/DIV
3406 G15
100
125
3406 G13
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LTC3406 LTC3406-1.5/LTC3406-1.8 TYPICAL PERFOR A CE CHARACTERISTICS
(From Figure 1a Except for the Resistive Divider Resistor Values) Start-Up from Shutdown
RUN 2V/DIV VOUT 2V/DIV
VOUT 100mV/DIV AC COUPLED IL 500mA/DIV
ILOAD 500mA/DIV
VIN = 3.6V VOUT = 1.8V ILOAD = 600mA
40s/DIV
Load Step
VOUT 100mV/DIV AC COUPLED
IL 500mA/DIV
ILOAD 500mA/DIV VIN = 3.6V 20s/DIV VOUT = 1.8V ILOAD = 100mA TO 600mA
3406 G19
PI FU CTIO S
RUN (Pin 1): Run Control Input. Forcing this pin above 1.5V enables the part. Forcing this pin below 0.3V shuts down the device. In shutdown, all functions are disabled drawing <1A supply current. Do not leave RUN floating. GND (Pin 2): Ground Pin. SW (Pin 3): Switch Node Connection to Inductor. This pin connects to the drains of the internal main and synchronous power MOSFET switches. VIN (Pin 4): Main Supply Pin. Must be closely decoupled to GND, Pin 2, with a 2.2F or greater ceramic capacitor. VFB (Pin 5) (LTC3406): Feedback Pin. Receives the feedback voltage from an external resistive divider across the output. VOUT (Pin 5) (LTC3406-1.5/LTC3406-1.8): Output Voltage Feedback Pin. An internal resistive divider divides the output voltage down for comparison to the internal reference voltage.
UW
Load Step
VOUT 100mV/DIV AC COUPLED
Load Step
IL 500mA/DIV ILOAD 500mA/DIV
VIN = 3.6V 20s/DIV VOUT = 1.8V ILOAD = 0mA TO 600mA
3406 G17
ILOAD 500mA/DIV
3406 G16
VIN = 3.6V 20s/DIV VOUT = 1.8V ILOAD = 50mA TO 600mA
3406 G18
Load Step
VOUT 100mV/DIV AC COUPLED
IL 500mA/DIV
ILOAD 500mA/DIV VIN = 3.6V 20s/DIV VOUT = 1.8V ILOAD = 200mA TO 600mA
3406 G20
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LTC3406 LTC3406-1.5/LTC3406-1.8
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0.65V OSC 4 VIN
VFB /VOUT 5 LTC3406-1.5 R1 + R2 = 550k LTC3406-1.8 R1 + R2 = 540k R1 FB R2 0.6V
VIN RUN 1 0.6V REF
SHUTDOWN
OPERATIO
(Refer to Functional Diagram)
Main Control Loop The LTC3406 uses a constant frequency, current mode step-down architecture. Both the main (P-channel MOSFET) and synchronous (N-channel MOSFET) switches are internal. During normal operation, the internal top power MOSFET is turned on each cycle when the oscillator sets the RS latch, and turned off when the current comparator, ICOMP, resets the RS latch. The peak inductor current at which ICOMP resets the RS latch, is controlled by the output of error amplifier EA. When the load current increases, it causes a slight decrease in the feedback voltage, FB, relative to the 0.6V reference, which in turn, causes the EA amplifier's output voltage to increase until the average inductor current matches the new load current. While the top MOSFET is off, the bottom MOSFET is turned on until either the inductor current starts to reverse, as indicated by the current reversal comparator IRCMP, or the beginning of the next clock cycle.
Burst Mode Operation The LTC3406 is capable of Burst Mode operation in which the internal power MOSFETs operate intermittently based on load demand. In Burst Mode operation, the peak current of the inductor is set to approximately 200mA regardless of the output load. Each burst event can last from a few cycles at light loads to almost continuously cycling with short sleep intervals at moderate loads. In between these burst events, the power MOSFETs and any unneeded circuitry are turned off, reducing the quiescent current to 20A. In this sleep state, the load current is being supplied solely from the output capacitor. As the output voltage droops, the EA amplifier's output rises above the sleep threshold signaling the BURST comparator to trip and turn the top MOSFET on. This process repeats at a rate that is dependent on the load demand.
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-
IRCMP
+
-
+
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SLOPE COMP OSC
FREQ SHIFT
- +
EA 0.4V
- +
BURST S R Q Q
SLEEP
-
ICOMP
+
5
RS LATCH
SWITCHING LOGIC AND BLANKING CIRCUIT
ANTISHOOTTHRU
3 SW
2 GND
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LTC3406 LTC3406-1.5/LTC3406-1.8
OPERATIO
Short-Circuit Protection When the output is shorted to ground, the frequency of the oscillator is reduced to about 210kHz, 1/7 the nominal frequency. This frequency foldback ensures that the inductor current has more time to decay, thereby preventing runaway. The oscillator's frequency will progressively increase to 1.5MHz when VFB or VOUT rises above 0V. Dropout Operation As the input supply voltage decreases to a value approaching the output voltage, the duty cycle increases toward the maximum on-time. Further reduction of the supply voltage forces the main switch to remain on for more than one cycle until it reaches 100% duty cycle. The output voltage will then be determined by the input voltage minus the voltage drop across the P-channel MOSFET and the inductor. An important detail to remember is that at low input supply voltages, the RDS(ON) of the P-channel switch increases (see Typical Performance Characteristics). Therefore, the user should calculate the power dissipation when the LTC3406 is used at 100% duty cycle with low input voltage (See Thermal Considerations in the Applications Information section). Low Supply Operation The LTC3406 will operate with input supply voltages as low as 2.5V, but the maximum allowable output current is reduced at this low voltage. Figure 2 shows the reduction
MAXIMUM OUTPUT CURRENT (mA)
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(Refer to Functional Diagram)
in the maximum output current as a function of input voltage for various output voltages. Slope Compensation and Inductor Peak Current Slope compensation provides stability in constant frequency architectures by preventing subharmonic oscillations at high duty cycles. It is accomplished internally by adding a compensating ramp to the inductor current signal at duty cycles in excess of 40%. Normally, this results in a reduction of maximum inductor peak current for duty cycles > 40%. However, the LTC3406 uses a patent-pending scheme that counteracts this compensating ramp, which allows the maximum inductor peak current to remain unaffected throughout all duty cycles.
1200 1000 800 600 400 200 0 VOUT = 1.8V VOUT = 2.5V VOUT = 1.5V
2.5
3.0
3.5 4.0 4.5 SUPPLY VOLTAGE (V)
5.0
5.5
3406 F02
Figure 2. Maximum Output Current vs Input Voltage
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LTC3406 LTC3406-1.5/LTC3406-1.8
APPLICATIO S I FOR ATIO
The basic LTC3406 application circuit is shown in Figure 1. External component selection is driven by the load requirement and begins with the selection of L followed by CIN and COUT. Inductor Selection For most applications, the value of the inductor will fall in the range of 1H to 4.7H. Its value is chosen based on the desired ripple current. Large value inductors lower ripple current and small value inductors result in higher ripple currents. Higher VIN or VOUT also increases the ripple current as shown in equation 1. A reasonable starting point for setting ripple current is IL = 240mA (40% of 600mA).
IL =
V 1 VOUT 1 - OUT ( f)(L) VIN
The DC current rating of the inductor should be at least equal to the maximum load current plus half the ripple current to prevent core saturation. Thus, a 720mA rated inductor should be enough for most applications (600mA + 120mA). For better efficiency, choose a low DC-resistance inductor. The inductor value also has an effect on Burst Mode operation. The transition to low current operation begins when the inductor current peaks fall to approximately 200mA. Lower inductor values (higher IL) will cause this to occur at lower load currents, which can cause a dip in efficiency in the upper range of low current operation. In Burst Mode operation, lower inductance values will cause the burst frequency to increase. Inductor Core Selection Different core materials and shapes will change the size/ current and price/current relationship of an inductor. Toroid or shielded pot cores in ferrite or permalloy materials are small and don't radiate much energy, but generally cost more than powdered iron core inductors with similar electrical characteristics. The choice of which style
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inductor to use often depends more on the price vs size requirements and any radiated field/EMI requirements than on what the LTC3406 requires to operate. Table 1 shows some typical surface mount inductors that work well in LTC3406 applications.
Table 1. Representative Surface Mount Inductors
PART NUMBER Sumida CDRH3D16 VALUE (H) 1.5 2.2 3.3 4.7 2.2 3.3 4.7 3.3 4.7 1.0 2.2 4.7 DCR ( MAX) 0.043 0.075 0.110 0.162 0.116 0.174 0.216 0.17 0.20 0.060 0.097 0.150 MAX DC SIZE CURRENT (A) W x L x H (mm3) 1.55 1.20 1.10 0.90 0.950 0.770 0.750 1.00 0.95 1.00 0.79 0.65 3.8 x 3.8 x 1.8 Sumida CMD4D06 Panasonic ELT5KT Murata LQH32CN 3.5 x 4.3 x 0.8 (1) 4.5 x 5.4 x 1.2 2.5 x 3.2 x 2.0
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CIN and COUT Selection In continuous mode, the source current of the top MOSFET is a square wave of duty cycle VOUT/VIN. To prevent large voltage transients, a low ESR input capacitor sized for the maximum RMS current must be used. The maximum RMS capacitor current is given by:
[VOUT (VIN - VOUT )]1/ 2 CIN required IRMS IOMAX
VIN This formula has a maximum at VIN = 2VOUT, where IRMS = IOUT/2. This simple worst-case condition is commonly used for design because even significant deviations do not offer much relief. Note that the capacitor manufacturer's ripple current ratings are often based on 2000 hours of life. This makes it advisable to further derate the capacitor, or choose a capacitor rated at a higher temperature than required. Always consult the manufacturer if there is any question.
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LTC3406 LTC3406-1.5/LTC3406-1.8
APPLICATIO S I FOR ATIO
The selection of COUT is driven by the required effective series resistance (ESR). Typically, once the ESR requirement for COUT has been met, the RMS current rating generally far exceeds the IRIPPLE(P-P) requirement. The output ripple VOUT is determined by:
1 VOUT IL ESR + 8fC OUT
where f = operating frequency, COUT = output capacitance and IL = ripple current in the inductor. For a fixed output voltage, the output ripple is highest at maximum input voltage since IL increases with input voltage. Aluminum electrolytic and dry tantalum capacitors are both available in surface mount configurations. In the case of tantalum, it is critical that the capacitors are surge tested for use in switching power supplies. An excellent choice is the AVX TPS series of surface mount tantalum. These are specially constructed and tested for low ESR so they give the lowest ESR for a given volume. Other capacitor types include Sanyo POSCAP, Kemet T510 and T495 series, and Sprague 593D and 595D series. Consult the manufacturer for other specific recommendations. Using Ceramic Input and Output Capacitors Higher values, lower cost ceramic capacitors are now becoming available in smaller case sizes. Their high ripple current, high voltage rating and low ESR make them ideal for switching regulator applications. Because the LTC3406's control loop does not depend on the output capacitor's ESR for stable operation, ceramic capacitors can be used freely to achieve very low output ripple and small circuit size. However, care must be taken when ceramic capacitors are used at the input and the output. When a ceramic capacitor is used at the input and the power is supplied by a wall adapter through long wires, a load step at the output can
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induce ringing at the input, VIN. At best, this ringing can couple to the output and be mistaken as loop instability. At worst, a sudden inrush of current through the long wires can potentially cause a voltage spike at VIN, large enough to damage the part. When choosing the input and output ceramic capacitors, choose the X5R or X7R dielectric formulations. These dielectrics have the best temperature and voltage characteristics of all the ceramics for a given value and size. Output Voltage Programming (LTC3406 Only) In the adjustable version, the output voltage is set by a resistive divider according to the following formula: R2 VOUT = 0.6 V 1 + R1
(2)
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The external resistive divider is connected to the output, allowing remote voltage sensing as shown in Figure 3.
0.6V VOUT 5.5V R2 VFB LTC3406 GND
3406 F03
R1
Figure 3. Setting the LTC3406 Output Voltage
Efficiency Considerations The efficiency of a switching regulator is equal to the output power divided by the input power times 100%. It is often useful to analyze individual losses to determine what is limiting the efficiency and which change would produce the most improvement. Efficiency can be expressed as: Efficiency = 100% - (L1 + L2 + L3 + ...) where L1, L2, etc. are the individual losses as a percentage of input power.
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LTC3406 LTC3406-1.5/LTC3406-1.8
APPLICATIO S I FOR ATIO
Although all dissipative elements in the circuit produce losses, two main sources usually account for most of the losses in LTC3406 circuits: VIN quiescent current and I2R losses. The VIN quiescent current loss dominates the efficiency loss at very low load currents whereas the I2R loss dominates the efficiency loss at medium to high load currents. In a typical efficiency plot, the efficiency curve at very low load currents can be misleading since the actual power lost is of no consequence as illustrated in Figure 4.
1 VOUT = 1.2V VOUT = 1.5V VOUT = 1.8V VOUT = 2.5V
0.1
POWER LOSS (W)
0.01
0.001
0.0001
0.00001 0.1
1
10 100 LOAD CURRENT (mA)
1000
3406 F04
Figure 4. Power Lost vs Load Current
1. The VIN quiescent current is due to two components: the DC bias current as given in the electrical characteristics and the internal main switch and synchronous switch gate charge currents. The gate charge current results from switching the gate capacitance of the internal power MOSFET switches. Each time the gate is switched from high to low to high again, a packet of charge, dQ, moves from VIN to ground. The resulting dQ/dt is the current out of VIN that is typically larger than the DC bias current. In continuous mode, IGATECHG = f(QT + QB) where QT and QB are the gate charges of the internal top and bottom switches. Both the DC bias and gate charge losses are proportional to VIN and thus their effects will be more pronounced at higher supply voltages.
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2. I2R losses are calculated from the resistances of the internal switches, RSW, and external inductor RL. In continuous mode, the average output current flowing through inductor L is "chopped" between the main switch and the synchronous switch. Thus, the series resistance looking into the SW pin is a function of both top and bottom MOSFET RDS(ON) and the duty cycle (DC) as follows: RSW = (RDS(ON)TOP)(DC) + (RDS(ON)BOT)(1 - DC) The RDS(ON) for both the top and bottom MOSFETs can be obtained from the Typical Performance Charateristics curves. Thus, to obtain I2R losses, simply add RSW to RL and multiply the result by the square of the average output current. Other losses including CIN and COUT ESR dissipative losses and inductor core losses generally account for less than 2% total additional loss. Thermal Considerations In most applications the LTC3406 does not dissipate much heat due to its high efficiency. But, in applications where the LTC3406 is running at high ambient temperature with low supply voltage and high duty cycles, such as in dropout, the heat dissipated may exceed the maximum junction temperature of the part. If the junction temperature reaches approximately 150C, both power switches will be turned off and the SW node will become high impedance. To avoid the LTC3406 from exceeding the maximum junction temperature, the user will need to do some thermal analysis. The goal of the thermal analysis is to determine whether the power dissipated exceeds the maximum junction temperature of the part. The temperature rise is given by: TR = (PD)(JA) where PD is the power dissipated by the regulator and JA is the thermal resistance from the junction of the die to the ambient temperature.
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LTC3406 LTC3406-1.5/LTC3406-1.8
APPLICATIO S I FOR ATIO
The junction temperature, TJ, is given by: T J = TA + TR where TA is the ambient temperature.
As an example, consider the LTC3406 in dropout at an input voltage of 2.7V, a load current of 600mA and an ambient temperature of 70C. From the typical performance graph of switch resistance, the RDS(ON) of the P-channel switch at 70C is approximately 0.52. Therefore, power dissipated by the part is: PD = ILOAD2 * RDS(ON) = 187.2mW For the SOT-23 package, the JA is 250C/ W. Thus, the junction temperature of the regulator is: TJ = 70C + (0.1872)(250) = 116.8C which is below the maximum junction temperature of 125C. Note that at higher supply voltages, the junction temperature is lower due to reduced switch resistance (RDS(ON)). Checking Transient Response The regulator loop response can be checked by looking at the load transient response. Switching regulators take several cycles to respond to a step in load current. When a load step occurs, VOUT immediately shifts by an amount equal to (ILOAD * ESR), where ESR is the effective series resistance of COUT. ILOAD also begins to charge or discharge COUT, which generates a feedback error signal. The regulator loop then acts to return VOUT to its steadystate value. During this recovery time VOUT can be monitored for overshoot or ringing that would indicate a stability problem. For a detailed explanation of switching control loop theory, see Application Note 76.
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A second, more severe transient is caused by switching in loads with large (>1F) supply bypass capacitors. The discharged bypass capacitors are effectively put in parallel with COUT, causing a rapid drop in VOUT. No regulator can deliver enough current to prevent this problem if the load switch resistance is low and it is driven quickly. The only solution is to limit the rise time of the switch drive so that the load rise time is limited to approximately (25 * CLOAD). Thus, a 10F capacitor charging to 3.3V would require a 250s rise time, limiting the charging current to about 130mA. PC Board Layout Checklist When laying out the printed circuit board, the following checklist should be used to ensure proper operation of the LTC3406. These items are also illustrated graphically in Figures 5 and 6. Check the following in your layout: 1. The power traces, consisting of the GND trace, the SW trace and the VIN trace should be kept short, direct and wide. 2. Does the VFB pin connect directly to the feedback resistors? The resistive divider R1/R2 must be connected between the (+) plate of COUT and ground. 3. Does the (+) plate of CIN connect to VIN as closely as possible? This capacitor provides the AC current to the internal power MOSFETs. 4. Keep the switching node, SW, away from the sensitive VFB node. 5. Keep the (-) plates of CIN and COUT as close as possible.
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LTC3406 LTC3406-1.5/LTC3406-1.8
APPLICATIO S I FOR ATIO
1 RUN VFB 5 R2 LTC3406 2
-
VOUT COUT
GND 4 CFWD
VOUT 2
+
3 L1
SW
VIN CIN
BOLD LINES INDICATE HIGH CURRENT PATHS
Figure 5a. LTC3406 Layout Diagram
VIA TO GND
R1 VIA TO VIN R2 CFWD VIN VIA TO VOUT
PIN 1 VOUT L1 SW LTC3406
COUT GND
CIN
3406 F06a
Figure 6a. LTC3406 Suggested Layout
Design Example As a design example, assume the LTC3406 is used in a single lithium-ion battery-powered cellular phone application. The VIN will be operating from a maximum of 4.2V down to about 2.7V. The load current requirement is a maximum of 0.6A but most of the time it will be in standby mode, requiring only 2mA. Efficiency at both low and high load currents is important. Output voltage is 2.5V. With this information we can calculate L using equation (1),
L= V 1 VOUT 1 - OUT ( f)(IL ) VIN
(3)
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R1
1 RUN LTC3406-1.8 5
W
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-
COUT
GND VOUT SW VIN CIN
+
VIN
3 L1
4
VIN
3406 F05b
3406 F05a
BOLD LINES INDICATE HIGH CURRENT PATHS
Figure 5b. LTC3406-1.8 Layout Diagram
VIA TO VOUT VIA TO VIN
VIN
PIN 1 VOUT L1 SW LTC3406-1.8
COUT GND
CIN
3406 F06b
Figure 6b. LTC3406-1.8 Suggested Layout
Substituting VOUT = 2.5V, VIN = 4.2V, IL = 240mA and f = 1.5MHz in equation (3) gives: L= 2.5V 2.5V 1 - = 2.81H 1.5MHz(240mA) 4.2V
A 2.2H inductor works well for this application. For best efficiency choose a 720mA or greater inductor with less than 0.2 series resistance. CIN will require an RMS current rating of at least 0.3A ILOAD(MAX)/2 at temperature and COUT will require an ESR of less than 0.25. In most cases, a ceramic capacitor will satisfy this requirement.
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LTC3406 LTC3406-1.5/LTC3406-1.8
APPLICATIO S I FOR ATIO
For the feedback resistors, choose R1 = 316k. R2 can then be calculated from equation (2) to be: V R2 = OUT - 1 R1 = 1000k 0.6
EFFICIENCY (%)
VIN 2.7V TO 4.2V
4 CIN 2.2F CER 1
VIN
SW
3
2.2H* 22pF
LTC3406 RUN GND 2 VFB 5 1M 316k
3406 F07a
*MURATA LQH32CN2R2M33 ** TAIYO YUDEN JMK316BJ106ML TAIYO YUDEN LMK212BJ225MG
Figure 7a
TYPICAL APPLICATIO S
Single Li-Ion 1.5V/600mA Regulator for High Efficiency and Small Footprint
VIN 2.7V TO 4.2V 4 CIN** 4.7F CER VIN RUN VOUT GND 2 *MURATA LQH32CN2R2M33 **TAIYO YUDEN JMK212BJ475MG TAIYO YUDEN JMK316BJ106ML 5
3406 TA05
95 90 85
VOUT = 1.5V VIN = 2.7V VIN = 4.2V
VOUT 100mV/DIV AC COUPLED IL 500mA/DIV
EFFICIENCY (%)
80 VIN = 3.6V 75 70 65 60 0.1
ILOAD 500mA/DIV VIN = 3.6V 20s/DIV VOUT = 1.5V ILOAD = 0A TO 600mA
1 10 100 OUTPUT CURRENT (mA) 1000
3406 TA06
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Figure 7 shows the complete circuit along with its efficiency curve.
100 95 90 VIN = 3.6V 85 80 75 70 65 60 0.1 1 10 100 OUTPUT CURRENT (mA) 1000
3406 F07b
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VOUT = 2.5V VIN = 2.7V
VOUT 2.5V COUT** 10F CER
VIN = 4.2V
Figure 7b
SW
3
2.2H* COUT1 10F CER
VOUT 1.5V
LTC3406-1.5 1
VOUT 100mV/DIV AC COUPLED
IL 500mA/DIV
ILOAD 500mA/DIV
3406 TA07
VIN = 3.6V 20s/DIV VOUT = 1.5V ILOAD = 200mA TO 600mA
3406 TA08
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LTC3406 LTC3406-1.5/LTC3406-1.8
TYPICAL APPLICATIO S
Single Li-Ion 1.2V/600mA Regulator for High Efficiency and Small Footprint
VIN 2.7V TO 4.2V 4 CIN 2.2F CER 1 3 2.2H* 22pF VOUT 1.2V COUT** 10F CER 301k 301k
3406 TA09
95 90 85
EFFICIENCY (%)
VOUT = 1.2V VIN = 2.7V
80 75 70 65 60 0.1
VIN = 4.2V VIN = 3.6V
1 10 100 OUTPUT CURRENT (mA)
3406 TA10
VIN 5V
100
VIN = 5V 95 VOUT = 3.3V 90
EFFICIENCY (%)
85 80 75 70 65 60 0.1 10 100 1 OUTPUT CURRENT (mA) 1000
3406 TA14
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VIN
SW
LTC3406 RUN GND 2 VFB 5
*MURATA LQH32CN2R2M33 ** TAIYO YUDEN JMK316BJ106ML TAIYO YUDEN LMK212BJ225MG
VOUT 100mV/DIV AC COUPLED IL 500mA/DIV
VOUT 100mV/DIV AC COUPLED
IL 500mA/DIV
ILOAD 500mA/DIV VIN = 3.6V 20s/DIV VOUT = 1.2V ILOAD = 0mA TO 600mA
1000
3406 TA11
ILOAD 500mA/DIV VIN = 3.6V 20s/DIV VOUT = 1.2V ILOAD = 200mA TO 600mA
3406 TA12
Tiny 3.3V/600mA Buck Regulator
4 CIN 4.7F CER 1
VIN
SW
3
2.2H* 22pF COUT** 10F CER 301k 66.5k
3406 TA13
VOUT 3.3V 600mA
LTC3406 RUN GND 2 VFB 5
*MURATA LQH32CN2R2M33 ** TAIYO YUDEN JMK316BJ106ML TAIYO YUDEN JMK212BJ475MG
VOUT 100mV/DIV AC COUPLED IL 500mA/DIV
ILOAD 500mA/DIV VIN = 5V 20s/DIV VOUT = 3.3V ILOAD = 200mA TO 600mA
3406 TA15
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LTC3406 LTC3406-1.5/LTC3406-1.8
PACKAGE DESCRIPTIO
0.62 MAX
0.95 REF
3.85 MAX 2.62 REF
RECOMMENDED SOLDER PAD LAYOUT PER IPC CALCULATOR
0.20 BSC 1.00 MAX DATUM `A'
0.30 - 0.50 REF 0.09 - 0.20 (NOTE 3) NOTE: 1. DIMENSIONS ARE IN MILLIMETERS 2. DRAWING NOT TO SCALE 3. DIMENSIONS ARE INCLUSIVE OF PLATING 4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR 5. MOLD FLASH SHALL NOT EXCEED 0.254mm 6. JEDEC PACKAGE REFERENCE IS MO-193
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
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S5 Package 5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635)
2.90 BSC (NOTE 4) 1.22 REF 1.4 MIN 2.80 BSC 1.50 - 1.75 (NOTE 4) PIN ONE 0.30 - 0.45 TYP 5 PLCS (NOTE 3) 0.95 BSC 0.80 - 0.90 0.01 - 0.10 1.90 BSC
S5 TSOT-23 0302
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LTC3406 LTC3406-1.5/LTC3406-1.8
TYPICAL APPLICATIO
Single Li-Ion 1.8V/600mA Regulator for Low Output Ripple and Small Footprint
VIN 2.7V TO 4.2V 4 CIN** 4.7F CER VIN RUN VOUT GND 2 *MURATA LQH32CN4R7M34 **TAIYO YUDEN CERAMIC JMK212BJ475MG SANYO POSCAP 4TPB100M 5
3406 TA01
95 90 85
VOUT = 1.8V
EFFICIENCY (%)
VIN = 2.7V VIN = 3.6V VIN = 4.2V
80 75 70 65 60 0.1
1 10 100 OUTPUT CURRENT (mA)
1000
3406 TA02
RELATED PARTS
PART NUMBER LTC1474/LTC1475 LT1616 LTC1701 LTC1767 LTC1779 LTC1875 LTC1877 LTC1878 LTC1879 LTC3404 LTC3405/LTC3405A LTC3405A-1.5 LTC3405A-1.8 LTC3406B LTC3406B-1.5 LTC3406B-1.8 LTC3411 LTC3412 DESCRIPTION 250mA (IOUT) Low Quiescent Current Step-Down DC/DC Converters 1.4MHz, 600mA Step-Down DC/DC Converter 1MHz, 500mA (IOUT) Step-Down DC/DC Converter 1.5A, 1.25MHz Step-Down Switching Regulator 550kHz, 250mA (IOUT) Step-Down Switching Regulator 550kHz, 1.2A (IOUT) Synchronous Step-Down Regulator 550kHz, 600mA (IOUT) Synchronous Step-Down Regulator 550kHz, 600mA (IOUT) Synchronous Step-Down Regulator 550kHz, 1.2A (IOUT) Synchronous Step-Down Regulator 1.4MHz, 600mA (IOUT) Synchronous Monolithic Step-Down Regulator 1.5MHz, 300mA (IOUT) Synchronous Monolithic Step-Down Regulators 1.5MHz, 600mA (IOUT) Synchronous Monolithic Step-Down Regulators 4MHz, 1.25A (IOUT) Synchronous Monolithic Step-Down Regulator 4MHz, 2.5A (IOUT) Synchronous Monolithic Step-Down Regulator COMMENTS VIN: 3V to 18V, Constant Off-Time, IQ = 10A, MS8 Package VIN: 3.6V to 25V, IQ = 1.9mA, ThinSOT Package VIN: 2.5V to 5.5V, Constant Off-Time, IQ = 135A, ThinSOT Package VIN: 3V to 25V, IQ = 1mA, MS8/E Packages VIN: 2.5V to 9.8V, IQ = 135A, ThinSOT Package VIN: 2.7V to 6V, IQ = 15A, TSSOP-16 Package VIN: 2.65V to 10V, IQ = 10A, MS8 Package VIN: 2.65V to 6V, IQ = 10A, MS8 Package VIN: 2.7V to 10V, IQ = 15A, TSSOP-16 Package Up to 95% Efficiency, VIN: 2.65V to 6V, IQ = 10A, MS8 Package Up to 95% Efficiency, VIN: 2.5V to 5.5V, IQ = 20A, Fixed Output Voltages Available, ThinSOT Package Up to 95% Efficiency, with Pulse Skipping Mode Fixed Output Voltages Available, ThinSOT Package Up to 95% Efficiency, VIN: 2.5V to 5.5V, IQ = 60A, MS Package Up to 95% Efficiency, VIN: 2.5V to 5.5V, IQ = 60A, TSSOP Package
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Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 FAX: (408) 434-0507
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SW 3 4.7H* VOUT 1.8V LTC3406-1.8 1
+
COUT1 100F
VOUT 100mV/DIV AC COUPLED
VOUT 100mV/DIV AC COUPLED
IL 500mA/DIV
IL 500mA/DIV
ILOAD 500mA/DIV VIN = 3.6V 40s/DIV VOUT = 1.8V ILOAD = 0mA TO 600mA
3406 TA03
ILOAD 500mA/DIV VIN = 3.6V 40s/DIV VOUT = 1.8V ILOAD = 200mA TO 600mA
3406 TA04
LT/TP 0604 1K REV A * PRINTED IN USA
www.linear.com
(c) LINEAR TECHNOLOGY CORPORATION 2002

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